Our key concerns are the overall attenuation level at midrange and the transition frequencies between bass, midrange, and treble. Greater midrange attenuation facilitates possible bass and treble boost, but requires greater overall voltage gain in the signal chain. The transition frequencies determine the frequency ranges that can be boosted or attenuated.

To convert our theoretical knowledge into a practical strategy we translate the equations that determine frequency response based on parts values into equations that determine parts values based on the desired frequency response. I'll demonstrate this using a concrete example. For design goals I'll set the mid-range attenuation to 8dB at maximum control settings, the bass-to-midrange transition to 500Hz, and the midrange-to-treble transition to 1kHz. With the controls at minimum I'll choose a flatter response than the Orange Graphic and set the bass-to-midrange transition to 200Hz and the midrange-to-treble transition to 1.4kHz.

Midrange attenuation is determined by **R _{1}** and

This means the value of **R _{2}** as a function of midrange attenuation

For minus 8dB the voltage gain is

for which we get a value of **R _{2} = 66k**. (We'll use 68k, the closest common part value.)

With the bass control at maximum, gain changes by at most 6dB per octave. This can't be altered - it's the basic nature of the circuit. So when we set the midrange attenuation and one of the bass transition frequencies, we effectively select the other as well. The bass-to-midrange transition frequency is given by

The capacitor value needed is thus

For our design goal of 500 Hz, for example, we get **C _{2} = 4700pF**. This puts the lower-bass transition frequency at

which is 202 Hz. Above this frequency the response transitions to its midrange value, decreasing at a rate of 6dB per octave until we reach 500 Hz. Here is the bass response, bass control at maximum, for **R _{1} = R_{3} = 100k**,

The midrange-treble Transition Frequency is

The value of **C _{3}** based on the desired transition frequency is thus

For 1kHz we get **C _{3} = 460pF**. (We'll use 470pF.) Here is the treble response with the control set to maximum:

Here is the superposition of the bass and treble response curves:

Our Bode plots and part value calculations assume a zero-impedance source, infinite-impedance tone controls, and an infinite-impedance load. Here is the actual response using Electronics Workbench Multisim®. The plot assumes a Fender Bassman environment with 1M tone controls. The source impedance is a 12AX7 cathode follower with an output impedance of 500 ohms and the driven stage is a long-tailed-pair phase inverter with an input impedance of 3M.

(The horizontal axis is a log scale of frequency from 10Hz to 10kHz and the vertical scale is from -15dB to 0dB.) The next plot below assumes the tone stack is driven by a 12AX7 voltage amplifier with an output impedance of 39k and a follow-on grid resistor representing an input impedance of 1M.

There is greater overall attenuation and a slight shift upward in the frequency at which gain is minimum, but the response is not dramatically different.

Here are the formulas we derived earlier for the bass-midrange and midrange-treble transition frequencies when the tone controls are set to minimum:

The first is the bass-midrange transition frequency and the second is the midrange-treble transition frequency. Turning these around we get

For our design goals of 200Hz and 1.4kHz we get **C _{4} = 4700pF** and

Here is the response when both controls are set to minimum:

Here is the response using Electronics Workbench Multisim®. The plot below assumes a Fender Bassman environment with 1M tone controls. The source impedance is a 12AX7 cathode follower with an output impedance of 500 ohms and the driven stage is a long-tailed-pair phase inverter with an input impedance of 3M.

(The horizontal axis is a log scale of frequency from 10Hz to 10kHz and the vertical scale is from -50dB to 0dB.) The next plot below assumes the tone stack is driven by a 12AX7 voltage amplifier with an output impedance of 39k and a follow-on grid resistor representing an input impedance of 1M.

Here is the final circuit:

If you're getting a feeling of déjà vu, it's probably because these parts values are identical to those found in the Garnet G250TR and G250D amplifiers.

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